Method and apparatus for time-domain droop control with integrated phasor current control

ABSTRACT

A method and apparatus for power converter current control. In one embodiment, the method comprises controlling an instantaneous current generated by a power converter such that that power converter appears, from the perspective of an AC line coupled to the power converter, as a virtual AC voltage source in series with a virtual impedance.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.16/016,745, entitled “Method and Apparatus for Time-Domain Droop Controlwith Integrated Phasor Current Control” and filed on Jun. 25, 2018,which is a continuation of U.S. patent application Ser. No. 15/048,651,entitled “Method and Apparatus for Time-Domain Droop Control withIntegrated Phasor Current Control” and filed on Feb. 19, 2016, whichclaims priority to U.S. Provisional Patent Application No. 62/118,230,entitled “Time-domain Droop Control with Integrated Phasor CurrentLimiting” and filed on Feb. 19, 2015. Each of the aforementioned patentapplications is herein incorporated in its entirety by reference.

BACKGROUND OF THE INVENTION Field of the Invention

Embodiments of the present disclosure relate generally to droop controland, more particularly, to droop control for a plurality of powerconverters.

Description of the Related Art

Droop control is an industry standard technique for autonomously sharingload among parallel AC generators/inverters proportional to their powerratings or operating costs. The technique relies on using small changesin voltage and frequency to dictate changes in real and reactive powerlevels. The “phase shift virtual impedance droop control” method is atime-domain implementation of droop control by which the converter iscontrolled to appear as a virtual AC voltage source in series with avirtual impedance, where the virtual AC voltage source has a constantamplitude and is phase-shifted proportional to the error between themeasured grid frequency and the nominal grid frequency.

This technique has several advantages including improved dynamicresponse and harmonic compensation; however, the method loses directcontrol of real and reactive currents and thus makes it difficult toimpose current limits. Current limits are necessary to constrain theconverter to a safe or desired operating region. For example, if thevirtual source voltage phasor commanded during droop control wouldresult in a real or reactive current phasor that exceeds the maximumcapability of the converter, the converter could be damaged or be forcedto shut-down. In addition, by not having direct phasor control of thereal and reactive currents, a converter cannot be operated with avirtual impedance while grid connected, resulting in disjointedtransitions between islanded and grid-connected states.

Therefore, there is a need in the art for time-domain droop control thatincludes indirect control of phasor currents.

SUMMARY OF THE INVENTION

Embodiments of the present invention generally relate to power convertercurrent control substantially as shown in and/or described in connectionwith at least one of the figures, as set forth more completely in theclaims.

These and other features and advantages of the present disclosure may beappreciated from a review of the following detailed description of thepresent disclosure, along with the accompanying figures in which likereference numerals refer to like parts throughout.

BRIEF DESCRIPTION OF THE DRAWINGS

So that the manner in which the above recited features of the presentinvention can be understood in detail, a more particular description ofthe invention, briefly summarized above, may be had by reference toembodiments, some of which are illustrated in the appended drawings. Itis to be noted, however, that the appended drawings illustrate onlytypical embodiments of this invention and are therefore not to beconsidered limiting of its scope, for the invention may admit to otherequally effective embodiments.

FIG. 1 is a block diagram of a system for power conversion using one ormore embodiments of the present invention;

FIG. 2 is a block diagram of a controller coupled to a PLL in accordancewith one or more embodiments of the present invention;

FIG. 3 is a block diagram of a virtual voltage in series with a virtualimpedance in accordance with one or more embodiments of the presentinvention;

FIG. 4 is a flow diagram of a method for current control in a powerconverter in accordance with one or more embodiments of the presentinvention; and

FIG. 5 is a flow diagram of a method for determining acurrent-controlled virtual voltage source waveform in accordance withone or more embodiments of the present invention.

DETAILED DESCRIPTION

FIG. 1 is a block diagram of a system 100 for power conversion using oneor more embodiments of the present invention. This diagram only portraysone variation of the myriad of possible system configurations anddevices that may utilize the present invention.

The system 100 is a microgrid that can operate in both an islanded stateand in a grid-connected state (i.e., when connected to another powergrid (such as one or more other microgrids and/or a commercial powergrid). The system 100 comprises a plurality of power converters 102-1,102-2, 102-3 . . . 102-N, collectively referred to as power converters102; a plurality of power sources 104-1, 104-2, 104-3 . . . 104-N,collectively referred to as power sources 104; a system controller 106;a bus 108; a load center 110; and an island interconnect device (IID)140 (which may also be referred to as a microgrid interconnect device(MID)). In some embodiments, such as the embodiment described below, thepower converters 102 are DC-AC inverters and the power sources 104 areDC power sources. The DC power sources 104 may be any suitable DCsource, such as an output from a previous power conversion stage, abattery, a renewable energy source (e.g., a solar panel or photovoltaic(PV) module, a wind turbine, a hydroelectric system, or similarrenewable energy source), or the like, for providing DC power. In otherembodiments the power converters 102 may be other types of converters(such as AC-AC matrix converters), and the power sources may be othertypes of power sources (such as AC power sources).

Each power converter 102-1, 102-2, 102-3 . . . 102-N is coupled to a DCpower source 104-1, 104-2, 104-3 . . . 104-N, respectively, in aone-to-one correspondence, although in some other embodiments multipleDC power sources 104 may be coupled to one or more of the powerconverters 102. Each of the power converters 102-1, 102-2, 102-3 . . .102-N comprises a corresponding controller 114-1, 114-2, 114-3 . . .114-N (collectively referred to as controllers 114) for controllingoperation of the corresponding power converter 102-1, 102-2, 102-3 . . .102-N, and a corresponding phase lock loop (PLL) 160-1, 160-2, 160-3 . .. 160-N (collectively referred to as PLLs 160). Each PLL 160 receivessamples of the voltage on the bus 108 (e.g., from a voltage samplercoupled to the bus 108), generates a signal indicative of the busvoltage waveform (amplitude, phase and frequency), and couples thegenerated signal to the corresponding controller 114.

The power converters 102 are coupled to the system controller 106 viathe bus 108 (which also may be referred to as an AC line or a grid). Thesystem controller 106 generally comprises a CPU coupled to each ofsupport circuits and a memory that comprises a system control module forcontrolling some operational aspects of the system 100 and/or monitoringthe system 100 (e.g., issuing certain command and control instructionsto one or more of the power converters 102, collecting data related tothe performance of the power converters 102, and the like). Thecontroller 106 is capable of communicating with the power converters 102by wireless and/or wired communication (e.g., power line communication)for providing certain operative control and/or monitoring of the powerconverters 102.

In some embodiments, the system controller 106 may be a gateway thatreceives data (e.g., performance data) from the power converters 102 andcommunicates the data and/or other information to a remote device orsystem, such as a master controller (not shown). Additionally oralternatively, the gateway may receive information from a remote deviceor system (not shown) and may communicate the information to the powerconverters 102 and/or use the information to generate control commandsthat are issued to the power converters 102.

The power converters 102 are coupled to the load center 110 via the bus108, and the load center 110 is coupled to the power grid via the IID140. When coupled to the power grid via the IID 140, the system 100 maybe referred to as grid-connected; when disconnected from the power gridvia the IID 140, the system 100 may be referred to as islanded. The IID140 determines when to disconnect from/connect to the power grid andperforms the disconnection/connection. For example, the IID 140 maydetect a grid fluctuation, disturbance or outage and, as a result,disconnect the system 100 from the power grid. Once disconnected fromthe power grid, the system 100 can continue to generate power as anintentional island, without imposing safety risks on any line workersthat may be working on the grid, using the droop control techniquesdescribed herein. The IID 140 comprises a disconnect component (e.g., adisconnect relay) for physically disconnecting/connecting the system 100from/to the power grid. In some embodiments, the IID 140 mayadditionally comprise an autoformer for coupling the balanced powersystem 100 to a split-phase load that may have a misbalance in it withsome neutral current.

In certain embodiments, the system controller 106 comprises the IID 140or a portion of the IID 140. For example, the system controller 106 maycomprise an islanding module for monitoring the power grid, detectinggrid failures and disturbances, determining when to disconnectfrom/connect to the power grid, and driving a disconnect componentaccordingly, where the disconnect component may be part of the systemcontroller 106 or, alternatively, separate from the system controller106. In other embodiments, such as the embodiment depicted in FIG. 1,the IID 140 is separate from the system controller 106 and comprises adisconnect component as well as a CPU and an islanding module formonitoring the power grid, detecting grid failures and disturbances,determining when to disconnect from/connect to the power grid, anddriving the disconnect component accordingly. In some embodiments, theIID 140 may coordinate with the system controller 106, e.g., using powerline communications. Thus, the disconnection/connection of the system100 to the power grid is a controlled process driven by the IID 140.

In one or more embodiments, the system 100 may additionally comprise oneor more energy storage/delivery devices (e.g., batteries) coupled to oneor more additional power converters 102 in a one-to-one correspondence,and the additional power converters 102 are also coupled to the bus 108.In such embodiments, the additional power converters 102 coupled to theenergy storage/delivery devices are bidirectional converters that canconvert power from the bus 108 for storage in the corresponding energystorage/delivery device and can convert energy stored in thecorresponding energy storage/delivery device to an output power that iscoupled to the bus 108. The combination of a power converter 102 andcorresponding energy storage/delivery device may be referred to as an“AC battery”.

The power converters 102 convert the DC power from the DC power sources104 to AC output power and couple the generated output power to the loadcenter 110 via the bus 108. The power is then distributed to one or moreloads (for example to one or more appliances) and/or to the power grid(when connected to the power grid); additionally or alternatively, thegenerated energy may be stored for later use, for example usingbatteries, heated water, hydro pumping, H₂O-to-hydrogen conversion, orthe like. Generally the system 100 is coupled to the commercial powergrid, although in some embodiments the system 100 is completely separatefrom the commercial grid and operates as an independent microgrid.

In accordance with one or more embodiments of the present invention, thepower converters 102 each employ a virtual voltage-virtual impedancecontrol technique that controls the power converter 102, by controllingthe instantaneous current, in such a way as to make the power converter102 appear (from the perspective of the power grid) as a virtual ACvoltage source in series with a virtual impedance as described herein.Although the virtual voltage-virtual impedance technique is generallyused for islanded systems, it can also be used when grid-connected so asto enable a seamless transition (i.e., no loss of power) betweengrid-connected and islanded states. In some alternative embodiments thepower converters 102 may employ a different technique for currentinjection when the system 100 is grid-connected.

While the technique described herein allows indirect limiting of phasorcurrent amplitude through strategic modification of the virtual sourceamplitude and phase, the instantaneous current could exceed limitsduring transients due to the transient voltage being applied directlyacross the virtual impedance. For this reason, an instantaneous currentlimit may also be employed so as to maintain the converter withincertain operating constraints even during transients.

During operation, each power converter 102 (i.e., the correspondingcontrol module 114) determines desired real and reactive phasor currentvalues to be generated using a droop technique and also determinesdesired real and reactive phasor currents to be generated based on oneor more current limiting techniques (such as maximum power pointtracking (MPPT), one or more economic optimizations (e.g., time of use(TOU)), charge control, advanced grid functions, demand response, andthe like).

Any droop technique where the desired real and reactive phasor currentsare determined as a function of grid voltage and frequency may beemployed for determining desired real and reactive phasor currentvalues, such as phase-shifted virtual voltage-virtual impedance droop,volt-var-frequency-watt droop, cross-coupled volt-var-frequency-wattdroop, non-linear droop, and the like. Droop equations employed by thedroop technique used may be offset as needed to achieve desiredobjectives when the system 100 is grid-connected (for example, tocontrol the net intertie to a residence) as well as when the system 100is islanded. When the system 100 is disconnected from the power grid(i.e., using the IID 140 or the system controller 106), the drooptechnique enables parallel operation of the power converters 102 withoutthe need for any common control circuitry or communication between thepower converters 102, thereby allowing the power converters 102 to sharethe load in a reliable manner when disconnected from the power grid.

The desired real and reactive phasor current values determined via thedroop technique are compared to one or more real and reactive currentthresholds, respectively, obtained via the current limiting techniques.Generally, the desired phasor current values determined from the currentlimiting techniques are used as the phasor current thresholds, althoughin other embodiments the thresholds may be determined differently. Ifone or both of the droop-determined desired phasor current valuesexceeds the corresponding threshold, it is then limited to a fixedlevel. For example, one or both of the droop-determined desired phasorcurrents from a power converter 102 may be greater than the powerconverter 102 can generate at that time (e.g., if the corresponding DCsource 104 is a PV module that is experiencing significant shading) andrequire a fixed limit to be applied.

The resulting controlled real and reactive phasor current values arethen used to determine a virtual voltage source waveform for generatingthe instantaneous current value. The instantaneous current value, whichspecifies the amount of current to be generated by the power converter102 at that moment in time, is used to drive power conversion by thepower converter 102 such that the power converter 102 emulates a virtualimpedance in the time domain while generating an amount of real andreactive current equal to the controlled real and reactive currentvalues. In those embodiments where phase-shifted virtual-voltage-virtualimpedance droop is used for determining the desired phasor currentvalues, this technique effectively modifies the original virtual sourceso as to indirectly impose phasor current limits. If the limits aren'treached, the resulting virtual voltage is the same as that which iscalculated from the original technique (i.e., without imposing anyphasor current limits).

In one or more embodiments, the current limiting is done by overwritingthe droop-determined desired real and/or reactive phasor current valueby a limited set point value determined from the current limitingtechniques (such as the maximum real and/or reactive current that thepower converter 102 is capable of generating at the time). When one ofthe phasor currents requires limiting, this technique producesinstantaneous currents driven by the power converter 102 such that, overeach grid cycle, one type of phasor current generated—either the real orreactive phasor current as set by the limited set point value—is limitedto a fixed amount while the other type of current is not and remainsdroop-controlled. If both of the droop-determined desired phasorcurrents require limiting, the droop-determined desired phasor currentvalues are each overwritten by a corresponding limited set point valueand the resulting instantaneous current drives the power converter 102such that both the real and reactive phasor currents are limited tofixed amounts.

The virtual voltage-virtual impedance control technique employed by thepower converters 102 integrates phasor-based current limiting into atime-domain approach that allows the phase/amplitude of the virtualvoltage source to be altered such that when either the desired realpower or the desired reactive power determined via the droop techniqueshould be limited, the corresponding real or reactive current phasorwill be a set value while the remaining desired current phasor remainsunchanged; if both the desired real and reactive phasor currents cannotbe provided, both are limited. The virtual voltage-virtual impedancecontrol technique keeps the control technique in the time domain forgood dynamic response and, when only one of the droop-determined real orreactive phasor current needs to be limited, maintains load sharing ofthe current that is not purposely being altered while allowing the othercurrent phasor to be set to a selected value. The virtualvoltage-virtual impedance control technique described herein isimplemented in each power converter 102 (i.e., by the correspondingcontrol module 114) and the algorithm is designed such that, whenislanded, the powers naturally converge as a result of each powerconverter 102 “seeing” the same AC waveform on the bus 108.

In some embodiments, the AC power generated by the power converters 102is single-phase AC power and each power converter 102 is controlled toappear as a single-phase virtual AC voltage source as described herein.In other embodiments, the power converters 102 generate three-phase ACpower and each power converter 102 is controlled to appear as athree-phase virtual AC voltage source as described herein.

In one or more embodiments, the system 100 may use the droop-controltechniques described herein following a black-start, for example asdescribed in commonly assigned, U.S. patent application Ser. No.15/047,337, filed Feb. 18, 2016, titled “Method and Apparatus forActivation and De-Activation of Power Conditioners in DistributedResource Island System Using Low Voltage AC”, which is hereinincorporated in its entirety by reference.

FIG. 2 is a block diagram of a controller 114 coupled to a PLL 160 inaccordance with one or more embodiments of the present invention. ThePLL 160 receives samples of the voltage on the bus 108 (e.g., from avoltage sampler coupled to the bus 108), generates a signal indicativeof the bus voltage waveform (amplitude, phase and frequency), andcouples the generated signal to the controller 114.

The controller 114 comprises support circuits 204 and a memory 206, eachcoupled to a central processing unit (CPU) 202. The CPU 202 may compriseone or more processors, microprocessors, microcontrollers andcombinations thereof configured to execute non-transient softwareinstructions to perform various tasks in accordance with embodiments ofthe present invention. The CPU 202 may additionally or alternativelyinclude one or more application specific integrated circuits (ASICs). Insome embodiments, the CPU 202 may be a microcontroller comprisinginternal memory for storing controller firmware that, when executed,provides the controller functionality herein. The controller 114 may beimplemented using a general purpose computer that, when executingparticular software, becomes a specific purpose computer for performingvarious embodiments of the present invention.

The support circuits 204 are well known circuits used to promotefunctionality of the CPU 202. Such circuits include, but are not limitedto, a cache, power supplies, clock circuits, buses, input/output (I/O)circuits, and the like. The controller 114 may be implemented using ageneral purpose computer that, when executing particular software,becomes a specific purpose computer for performing various embodimentsof the present invention. In one or more embodiments, the CPU 202 may bea microcontroller comprising internal memory for storing controllerfirmware that, when executed, provides the controller functionalitydescribed herein.

The memory 206 may comprise random access memory, read only memory,removable disk memory, flash memory, and various combinations of thesetypes of memory. The memory 206 is sometimes referred to as main memoryand may, in part, be used as cache memory or buffer memory. The memory206 generally stores the operating system (OS) 208, if necessary, of thecontroller 114 that can be supported by the CPU capabilities. In someembodiments, the OS 208 may be one of a number of commercially availableoperating systems such as, but not limited to, LINUX, Real-TimeOperating System (RTOS), and the like.

The memory 206 stores non-transient processor-executable instructionsand/or data that may be executed by and/or used by the CPU 202. Theseprocessor-executable instructions may comprise firmware, software, andthe like, or some combination thereof. The memory 206 stores variousforms of application software, such as a droop control module 216, acurrent limit module 218, a current control module 210 for determiningthe controlled real and reactive phasor current values as describedherein, a virtual voltage-virtual impedance module 212 for determiningthe instantaneous current as described herein, and a power conversionmodule 214 for driving the power converter 102 to generate theinstantaneous current.

The droop control module 216 determines the desired real and reactivephasor currents (i.e., the droop-determined desired phasor currents) byany suitable droop technique where the desired real and reactive phasorcurrent values are determined as a function of grid voltage andfrequency. Such droop techniques include volt-var-frequency-watt droopwhere la=Ka*(Frequency Error), lr=Kr*(Voltage Error); cross-coupledvolt-var-frequency-watt droop where la′=Ka*(Frequency Error),lr′=Kr*(Voltage Error), la=X/Z*la′+R/Z*lr, and lr=R/Z*la′+X/Z*lr′;non-linear droop; and the like. When operating in islanded mode, thedroop control module 216 calculates, for an ideal situation withunlimited resources, the desired amount of active and reactive phasorcurrents to be injected into the islanded grid to help support the grid.The current limits module 218 determines one or more desired phasorcurrents to be generated based on one or more current limitingtechniques (such as MPPT, economic optimizations, charge control,advanced grid functions, demand response, and the like) that manage thephysical limitations of the power conditioner 102 and/or the physicallimitations of the resource feeding that power conditioner 102. Thecurrent control module 210 applies the current limits to thedroop-determined desired phasor currents as necessary. Further detail onthe functionality provided by the droop module 216 and the currentcontrol module 210 is described below with respect to FIGS. 4 and 5;further detail on the functionality provided by the current limitsmodule 218 is described below with respect to FIG. 4.

In some embodiments the droop module 216 runs continuously—i.e., whenthe power conditioner 102 is islanded as well as when it isgrid-connected—and current limits determined from one or more currentlimiting techniques, such as MPPT, are then applied by the currentcontrol module 210 as applicable. Such operation allows a seamlesstransition between operating in an islanded state and operating in agrid-connected state. In some alternative embodiments, the desired realand reactive phasor currents are determined solely by the current limitsmodule 219 (e.g., by an MPPT or charge control technique) when the powerconditioner 102 is grid-connected, and, when the power conditioner 102is islanded, the droop module 216 operates to determine desired phasorcurrent values with limits from the current limits module 218 applied asnecessary by the current control module 210.

Further detail on the functionality provided by the virtualvoltage-virtual impedance module 212 is described below with respect toFIGS. 3 and 4—and further detail on the functionality provided by thecurrent control module 210 is described below with respect to FIGS. 4and 5 In various embodiments, one or more of the power conversion module214, the droop control module 216, the current limit module 218, thecurrent control module 210, and the virtual voltage-virtual impedancemodule 210, or portions thereof, are implemented in software, firmware,hardware, or a combination thereof.

The memory 206 additionally stores a database 220 for storing datarelated to the operation of the power converter 102 and/or the presentinvention, such as one or more thresholds, equations, formulas, curves,and/or algorithms for the control techniques described herein.

In some other embodiments, the PLL 160 may be part of the controller114; e.g., the PLL 160 may be a module within the memory 206.

FIG. 3 is a block diagram of a virtual voltage-virtual impedance circuit300 in accordance with one or more embodiments of the present invention.The virtual voltage-virtual impedance circuit 300 (also referred to asthe circuit 300) comprises a virtual voltage source 302 in series with avirtual source impedance 304. The series combination of the virtualvoltage source 302 and the virtual source impedance 304 (also referredto as virtual impedance 304) is coupled across a grid 306, and thevirtual voltage source 302 drives the current 308 to flow in the circuit300. The grid 306 may be an islanded grid (i.e., when the powerconverter 102 is disconnected from another power grid by the IID 140 andis in an islanded state) or the grid 306 may be an interconnected grid(i.e., when the power converter 102 is coupled to another power grid,such as a commercial power grid, via the IID 140).

In accordance with one or more embodiments of the present invention,each power converter 102 is controlled (by its corresponding controller114) to appear, from the perspective of the grid 306, as the virtualvoltage source 302 in series with the virtual impedance 304, where realand reactive phasor currents for the power converter 102 are indirectlycontrolled by modifying amplitude and phase of a virtual voltagewaveform that defines the virtual voltage source 302. Generally, eachpower converter 102 is controlled to imitate the virtual voltage source302 in series with the virtual source impedance 304 independent ofwhether the system 100 is islanded or grid-connected, thereby enabling aseamless transition between operating in a grid-connected environmentand an islanded environment, although in some alternative embodimentsthe power converters 102 employ a different control technique when thesystem 100 is coupled to the power grid.

The virtual voltage source 302 (i.e., the virtual voltage waveformrepresenting the virtual voltage source 302) is computed based oncontrolled phasor current values—e.g., real and reactive phasor currentvalues that have limits applied as necessary—to integrate indirectcontrol of active and reactive current phasors into the generation ofthe virtual voltage source 302. In some embodiments, the virtual voltagewaveform, which may also be referred to as the current-controlledvirtual voltage waveform, may be computed using Equation (13) describedbelow, although in other embodiments other equations where the virtualvoltage waveform is computed as a function of real and reactive phasorcurrent values, or as a function of modified real and reactive phasorcurrent values described below, may be used in order to apply phasorcurrent control as necessary.

The virtual voltage source 302, as defined by the current-controlledvirtual voltage waveform, is applied to the virtual impedance 304 inorder to determine the current 308, where the current 308 represents theamount of instantaneous current to be injected by the power converter102 into the bus 108 in real-time. In certain embodiments, the circuit300 depicts an implementation of the virtual voltage-virtual impedancemodule 212; i.e., the virtual voltage-virtual impedance module 212digitally simulates the circuit 300 to determine the instantaneouscurrent value. In one or more of such embodiments, the simulation mayrun at a frequency of 1 MHz and the instantaneous current value isupdated every microsecond.

In one or more embodiments, the current-controlled virtual voltagewaveform may be derived as described below using a phase-shift virtualimpedance droop technique where the virtual voltage source 302 isdefined as a sinusoidal voltage source having a constant amplitude andis phase-shifted from the grid frequency proportional to the differencebetween the measured grid frequency and the nominal grid frequency. Insome alternative embodiments, the voltage source amplitude may be setdifferently among one or more of the power converters 102.

In one or more particular embodiments, desired droop-determined phasorcurrents may be calculated from the measured voltage and frequency usingthe technique as follows. The amplitude of the virtual voltage source302 is set at the constant amplitude Uset, where Uset is the set pointvoltage for the system (i.e., the peak value of the nominal gridvoltage, for example √{square root over (2)}*240=339.4V for a 240V ACsystem). The angle of the virtual voltage source 302 is offset from thegrid angle θ by an amount ψ that is proportional by a gain factor of kto the error in the measured grid frequency f and the target frequencyf₀, where the factor k may be determined based on a desired magnitude offrequency change for operating the system.

For a single-phase AC system, the virtual voltage source 302 may beexpressed as the virtual voltage source waveform:Usrc=Uset*(sin(θ+ψ)  (1)

The measured grid angle 9 and the measured grid frequency f are obtainedfrom the PLL 160. For a three-phase AC system, the virtual voltagesource waveform is a three-phase waveform comprising the waveform inEquation (1) plus two additional waveforms as given by Equation (1) thatare then phase-shifted by 120° and 240°.

The virtual impedance 304 comprises a real (i.e., resistive) portion Rand a reactive portion X. Generally the ratio X/R is set to a fixedvalue, although in certain embodiments it may be dynamically changed,e.g., based on the state of the system 100. For example, in someembodiments the ratio X/R may be selected to match the impedance ratioat the point of common coupling (PCC) looking towards the power gridwhen grid connected, and when islanded the ratio X/R may then be set tomatch the ratio between frequency and voltage load governing. In someembodiments, the ratio X/R is set to equal 1, which provides gooddamping characteristics and results in voltage and frequency bothchanging as a function of real and reactive power.

In order to determine the virtual voltage source 302, values for thedesired real and reactive phasor currents are first determined andlimited as necessary, where the limits are obtained from one or morecurrent limiting techniques (such as MPPT, economic optimizations,charge control, advanced grid functions, or the like). The resultingcontrolled phasor current values are then used in computing the virtualvoltage source 302, for example as described below with respect toEquations (8)-(13).

In order to determine the instantaneous current value for driving thepower converter 102, the virtual voltage source waveform is updated toincorporate any necessary real and/or reactive phasor current limits.First, “modified” real and reactive currents la′ and lr′, respectively,are determined based on the standard phase shift virtual impedance droopcontrol technique:

$\begin{matrix}{{Ia}^{\prime} = \frac{{Uset}*{\sin(\psi)}}{Z}} & (2) \\{{Ir}^{\prime} = \frac{{{Uset}*{\cos(\psi)}} - {U1d}}{Z}} & (3)\end{matrix}$

where la′ and lr′ are the modified real and reactive phasor currents,respectively; Uset is the constant voltage amplitude set point for thesystem; Z is the overall magnitude of the virtual source impedance 304;ψ is proportional to the measured grid frequency f and the targetfrequency f₀, and U1d is the amplitude of the fundamental component ofthe grid (e.g., as determined by a PLL 160).

Next, values for the corresponding desired real and reactive phasorcurrents la and lr, respectively, required from the power converter aredetermined using the inverse of a known rotational transformation matrix

${T = \begin{bmatrix}\frac{X}{Z} & {- \frac{R}{Z}} \\\frac{R}{Z} & \frac{X}{Z}\end{bmatrix}},$where X is the amplitude of the reactive portion of the virtual sourceimpedance 304, R is the real (i.e. resistive) portion of the virtualsource impedance 304, and Z is the overall magnitude of the virtualsource impedance 304:

$\begin{matrix}{{Ia} = {{\frac{X}{Z}{Ia}^{\prime}} + {\frac{R}{Z}{Ir}^{\prime}}}} & (4) \\{{Ir} = {{{- \frac{R}{Z}}{Ia}^{\prime}} + {\frac{X}{Z}{Ir}^{\prime}}}} & (5)\end{matrix}$

Although the droop-determined desired phasor current values aredescribed above as being derived using the phase-shift virtual impedancedroop technique, in other embodiments they may be derived by other drooptechniques. For example, droop techniques such asvolt-var-frequency-watt, cross-coupled volt-var-frequency-watt,non-linear droop, or the like may be used.

Once the droop-determined desired phasor current values are determined,limits are imposed on the desired real and reactive current values laand lr as follows:if(la>real current threshold),{la(controlled)=laAbsMax}  (6a)if(la<−real current threshold),{la(controlled)=−laAbsMax}  (6b)if(lr>reactive current threshold),{lr(controlled)=lrAbsMax}  (7a)if(lr<−reactive current threshold),{lr(controlled)=−lrAbsMax}  (7b)

where laAbsMax and lrAbsMax are each fixed values; otherwise, thecontrolled phasor current value is equal to the correspondingdroop-determined desired phasor current value. Generally, the real andreactive current thresholds are equal to laAbsMax and lrAbsMax,respectively, where laAbsMax and lrAbsMax are obtained from one or morecurrent limiting techniques (such as MPPT, economic optimizations,charge control, advanced grid functions, or the like). In someembodiments though, the real and or reactive current threshold may bedifferent from the values of laAbsMax and lrAbsMax. Limiting is done inboth the positive and negative directions to account for power flow ineither direction in the power converters 102. In some alternativeembodiments, other algorithms maybe used to generate the controlledcurrent phasor values in addition to and/or in place of the currentlimiting shown in Equations (6)-(7).

Based on the limits imposed, the resulting controlled real and reactivephasor current values are used to determine new modified real andreactive currents la′(controlled) and lr′(controlled), respectively,using the rotational transformation matrix T:

$\begin{matrix}{{{Ia}^{\prime}({controlled})} = {{\frac{X}{Z}{{Ia}({controlled})}} - {\frac{R}{Z}{{Ir}({controlled})}}}} & (8) \\{{{Ir}^{\prime}({controlled})} = {{\frac{R}{Z}{{Ia}({controlled})}} + {\frac{X}{Z}{{Ir}({controlled})}}}} & (9)\end{matrix}$

As described above, Usrc=Uset*(sin(θ+ψ) is set by definition. In oneembodiment, a virtual voltage source waveform with limits imposed asnecessary (i.e., the current-controlled virtual voltage source waveform)is determined as follows:

$\begin{matrix}{{Usrc} = {{Uset}*( {\sin( {\theta + \psi} )} )}} & (10) \\{\mspace{50mu}{= {{Uset}*( {{\sin\;\psi\mspace{11mu}\cos\;\theta} + {\cos\;\psi\mspace{11mu}\sin\;\theta}} )}}} & (11) \\{\mspace{50mu}{= {{( {{Uset}*\sin\;\psi} )\cos\;\theta} + {( {{Uset}*\cos\;\psi} )\mspace{11mu}\sin\;\theta}}}} & (12)\end{matrix}$

where θ=the grid phase. Using la′ *Z=Uset*sin ψ and lr′*Z+Uld=Uset*cosψ, (from Equations (2) and (3) above), the current-controlled Usrc canbe computed as:Usrc(controlled)=(la′(controlled)*Z)*cos θ+(lr′(controlled)*Z+U1d)*sinθ  (13)

In some other embodiments, other derivations of Equation (13) may beused.

The computed current-controlled virtual voltage source waveform is thenused in simulating the virtual voltage-virtual impedance circuit 300 todetermine the instantaneous current value for controlling powerconversion by the power converter 102. As the cos θ, sin θ, and U1dterms are outputs from the PLL 160, the algorithm given by Equation (13)for Usrc contains no square root functions and minimal trigonometricfunctions and thus is a highly efficient algorithm for computation.

FIG. 4 is a flow diagram of a method 400 for current control in a powerconverter in accordance with one or more embodiments of the presentinvention. The power converter is part of a microgrid and receives inputpower from an input power source and generates an output power; in someembodiments, the power converter may be a bidirectional converter thatcan convert DC-AC and AC-DC. The microgrid may be a single-phase ACsystem or, alternatively, a three-phase AC system.

The power converter, along with other analogous power converters, iscoupled to an AC bus that is coupled to one or more loads (e.g., via aload center). In some embodiments, the power converter is a powerconverter 102 of the system 100 previously described, and the method 400comprises an implementation of the droop module 216, the current limitsmodule 218, the current control module 210, the virtual voltage-virtualimpedance module 212, and the power conversion module 214. Generally,the microgrid may be capable of operating in an islanded state as wellas in a grid-connected state, although in other embodiments, themicrogrid is completely separate from another power grid and operatesintentionally as an independent microgrid.

The method 400 starts at step 402 and proceeds to step 406. At step 406,the voltage and frequency of the grid are determined, for example by aPLL such as the PLL 160. In some embodiments the grid is an islandedgrid, while in other embodiments the grid is an interconnected grid. Insome alternative embodiments where the grid is an islanded grid, thevoltage and frequency may be determined after the power converterresumes operation following the grid disconnection, for examplefollowing a black-start as described in commonly assigned, U.S. patentapplication Ser. No. 15/047,337, filed Feb. 18, 2016, titled “Method andApparatus for Activation and De-Activation of Power Conditioners inDistributed Resource Island System Using Low Voltage AC.

The method 400 proceeds to steps 408 and 412. At step 408, desired realand reactive phasor currents for the power converter to generate aredetermined using a droop technique. The desired phasor currents may bedetermined by any suitable droop technique where the desired real andreactive phasor currents are determined as a function of grid voltageand frequency, such as phase shift virtual impedance droop technique,volt-var-frequency-watt droop, cross-coupled volt-var-frequency-wattdroop, non-linear droop; and the like. Droop equations employed by thedroop technique used may be offset as needed to achieve desiredobjectives when the microgrid is grid-connected (for example, to controlthe net intertie to a residence) as well as when the microgrid isislanded

At step 412, desired phasor currents are determined using one or morecurrent limiting techniques, such as MPPT, one or more economicoptimizations, charge control, advanced grid functions, or the like. Themethod 400 proceeds from steps 408 and 412 to step 414.

At step 414, a determination is made whether the droop-determine desiredreal phasor current value exceeds a real current threshold or is lessthan the negative of the real current threshold. Generally, the realcurrent threshold is equal to the absolute value of the maximum amountof real current that the power converter is capable of generating atthat time, where the maximum amount of real current is equal to thedesired real phasor current determined by one or more of the currentlimiting techniques. If the result of the determination is no, themethod 400 proceeds to step 418 where the controlled real phasor currentvalue (i.e., la(controlled)) is set to a fixed value, such as thedroop-determined desired real phasor current value. The method 400 thenproceeds to step 420.

If at step 414 the result of the determination is yes, that thedroop-determined desired real phasor current value exceeds the realcurrent threshold or is less than the negative of the real currentthreshold, the method 400 proceeds to step 416 where the controlledphasor current value (i.e., la(controlled)) is set to a fixed value.Generally, the fixed value is equal to the real current threshold whenthe droop-determined desired real phasor current value exceeds the realcurrent threshold, and the fixed value is equal to the negative of thereal current threshold when the droop-determined desired real phasorcurrent value is less than the negative of the real current threshold.The method 400 proceeds from step 416 to step 420.

At step 420, a determination is made whether the droop-determineddesired reactive current value exceeds a reactive current threshold oris less than the negative of the reactive current threshold. Generally,the reactive current threshold is equal to the absolute value of themaximum amount of reactive current that the power converter is capableof generating at that time, where the maximum amount of reactive currentis equal to the desired reactive phasor current determined by one ormore of the current limiting techniques. If the result of thedetermination is no, the method 400 proceeds to step 424 where thecontrolled reactive phasor current value (i.e., lr(controlled)) is setto the droop-determined desired reactive phasor current value. Themethod 400 proceeds to step 426.

If at step 420 the result of the determination is yes, that thedroop-determined desired reactive phasor current value exceeds thereactive current threshold or is less than the negative of the reactivecurrent threshold, the method 400 proceeds to step 422 where thecontrolled desired reactive phasor current value (i.e., lr(controlled))is set to a fixed value. Generally, the fixed value is equal to thereactive current threshold when the droop-determined desired reactivephasor current value exceeds the reactive current threshold, and thefixed value is equal to the negative of the reactive current thresholdwhen the droop-determined desired reactive phasor current value is lessthan the negative of the reactive current threshold. The method 400proceeds from step 422 to step 426.

At step 426, a current-controlled virtual voltage source waveform isdetermined using the controlled phasor current values la(controlled) andlr(controlled), for example as previously described with respect toEquations (8)-(13). In some embodiments, the step 406 is animplementation of the droop module 216, the step 412 is animplementation of the current limits module 218, and the steps 414-426are an implementation of the current control module 210. One particularembodiment of the steps 408 and 414-426 of the method 400 is describedbelow with respect to FIG. 5.

The method 400 proceeds from step 426 to step 428, where thecurrent-controlled virtual voltage source waveform is applied to avirtual impedance for determine the instantaneous current value to becommanded from the power converter, where the virtual impedance may bedetermined as previously described. In some embodiments, the step 428 isan implementation of the virtual voltage-virtual impedance module 212.

The method 400 proceeds to step 430, where the instantaneous currentvalue is used to control power generation by the power converter; i.e.,the power converter is commanded to inject an amount of current into thegrid in real time in accordance with the instantaneous current value,respectively. In some embodiments, step 430 is an implementation of thepower conversion module 214. The method 400 proceeds from step 430 tostep 432.

At step 432, a determination is made whether to continue operating. Ifthe result of the determination is yes, the method 400 returns to step406. In some embodiments, the method 400 is repeated every microsecond;i.e., the instantaneous current value commanded from the power converteris updated every microsecond.

If at step 432 the result of the determination is no, the method 400proceeds to step 434 where it ends.

FIG. 5 is a flow diagram of a method 500 for determining acurrent-controlled virtual voltage source waveform in accordance withone or more embodiments of the present invention. The current-controlledvirtual voltage source waveform is computed using controlled phasorcurrent values determined based on a phase shift virtual impedance drooptechnique. The current-controlled virtual voltage source waveform isused for determining instantaneous current values to be commanded from apower converter that is part of a microgrid (e.g., a power converter102), where the microgrid may either be grid-connected or islanded. Themethod 500 is one embodiment of the steps 408 and 414-426 of the method400.

The method 500 starts at step 502 and proceeds to step 504. At step 504,the virtual voltage source waveform is defined based on a standard phaseshift virtual impedance droop technique as previously described withrespect to in Equation (1). In some embodiments, the microgridcomprising the power converter is a single-phase AC system and thevirtual voltage source waveform is a single-phase AC waveform as inEquation (1). In other embodiments the microgrid is a three-phase ACsystem and the virtual voltage source waveform comprises the waveform inEquation (1) plus two additional waveforms as in Equation (1) that arethen phase-shifted by 120° and 240°.

The method 500 proceeds to step 506, where the droop-determined desiredreal and reactive phasor current values are determined as previouslydescribed with respect to Equations (2)-(5). At step 508, adetermination is made whether the droop-determined desired real phasorcurrent value exceeds a real current threshold or is less than thenegative of the real current threshold. In some embodiments, the realcurrent threshold is equal to the desired real phasor current valuedetermined from one or more current limiting techniques as previouslydescribed. If the result of the determination is no, the method 500proceeds to step 509, where the controlled real phasor current value(i.e., la(controlled)) is set to the droop-determined desired realphasor current value. The method 500 proceeds from step 509 to step 512.

If at step 508 the result of the determination is yes, that thedroop-determined desired real current phasor value exceeds the realcurrent threshold or is less than the negative of the real currentthreshold, the method 500 proceeds to step 510. At step 510, thecontrolled real current phasor value (i.e., la (controlled)) is set to afixed value. Generally, the fixed value is equal to the real currentthreshold when the droop-determined desired real phasor current valueexceeds the real current threshold, and the fixed value is equal to thenegative of the real current threshold when the droop-determined desiredreal phasor current value is less than the negative of the real currentthreshold. The method 500 proceeds from step 510 to step 512.

At step 512, a determination is made whether the droop-determineddesired reactive phasor current value exceeds a reactive currentthreshold or is less than the negative of the reactive currentthreshold. Generally, the reactive current threshold is equal to theabsolute value of the maximum amount of reactive current that the powerconverter is capable of generating at that time, where the maximumamount of reactive current is equal to the desired reactive phasorcurrent determined by one or more of the current limiting techniquespreviously described. If the result of the determination is no, themethod 500 proceeds to step 515 where the controlled reactive phasorcurrent value (i.e., lr(controlled)) is set to the droop-determineddesired reactive phasor current value. The method 500 proceeds from step515 to step 516.

If at step 512 the result of the determination is yes, that thedroop-determined desired reactive phasor current value exceeds thereactive current threshold or is less than the negative of the reactivecurrent threshold, the method 500 proceeds to step 514. At step 514, thecontrolled reactive phasor current value is set to a fixed value.Generally, the fixed value is equal to the reactive current thresholdwhen the droop-determined desired reactive phasor current value exceedsthe reactive current threshold, and the fixed value is equal to thenegative of the reactive current threshold when the droop-determineddesired reactive phasor current value is less than the negative of thereactive current threshold. The method 500 proceeds from step 514 tostep 516.

At step 516, a current-controlled virtual voltage source waveform isdetermined using the controlled phasor current values la(controlled) andlr(controlled), for example as previously described with respect toEquations (8)-(13). The method 500 proceeds to step 518 where it ends.

While the foregoing is directed to embodiments of the present invention,other and further embodiments of the invention may be devised withoutdeparting from the basic scope thereof, and the scope thereof isdetermined by the claims that follow.

The invention claimed is:
 1. A method for power converter currentcontrol, comprising: controlling an instantaneous current generated by apower converter such that that power converter appears, from theperspective of an AC line coupled to the power converter, as a virtualAC voltage source in series with a virtual impedance.
 2. The method ofclaim 1, wherein real and reactive phasor currents for the powerconverter are indirectly controlled.
 3. The method of claim 2, whereinthe real and reactive phasor currents are indirectly controlled bymodifying amplitude and phase of a virtual voltage waveform that definesthe virtual AC voltage source.
 4. The method of claim 1, wherein theconverter is controlled to imitate the virtual AC voltage source inseries with the virtual impedance independent of whether the powerconverter is islanded or grid-connected.
 5. The method of claim 1,wherein (i) when the power converter is islanded, the power converter iscontrolled to imitate the virtual AC voltage source in series with thevirtual impedance independent of whether the power converter is islandedor grid-connected, and (ii) when the power converter is grid-connected,the power converter is controlled by a different control technique. 6.The method of claim 1, wherein: a virtual voltage waveform representingthe virtual AC voltage source is computed based on controlled phasorcurrent values.
 7. The method of claim 1, wherein a virtual voltagewaveform representing the virtual AC voltage source is derived using aphase-shift virtual impedance droop technique where the virtual ACvoltage source is defined as a sinusoidal voltage source having aconstant amplitude and is phase-shifted from a grid frequencyproportional to a difference between a measured grid frequency and anominal grid frequency.
 8. An apparatus for power converter currentcontrol, comprising: a controller for controlling an instantaneouscurrent generated by a power converter such that that power converterappears, from the perspective of an AC line coupled to the powerconverter, as a virtual AC voltage source in series with a virtualimpedance.
 9. The apparatus of claim 8, wherein real and reactive phasorcurrents for the power converter are indirectly controlled.
 10. Theapparatus of claim 9, wherein the real and reactive phasor currents areindirectly controlled by modifying amplitude and phase of a virtualvoltage waveform that defines the virtual AC voltage source.
 11. Theapparatus of claim 8, wherein the power converter is controlled toimitate the virtual AC voltage source in series with the virtualimpedance independent of whether the power converter is islanded orgrid-connected.
 12. The apparatus of claim 8, wherein (i) when the powerconverter is islanded, the power converter is controlled to imitate thevirtual AC voltage source in series with the virtual impedanceindependent of whether the power converter is islanded orgrid-connected, and (ii) when the power converter is grid-connected, thepower converter is controlled by a different control technique.
 13. Theapparatus of claim 11, wherein: a virtual voltage waveform representingthe virtual AC voltage source is computed based on controlled phasorcurrent values.
 14. The apparatus of claim 8, wherein a virtual voltagewaveform representing the virtual AC voltage source is derived using aphase-shift virtual impedance droop technique where the virtual ACvoltage source is defined as a sinusoidal voltage source having aconstant amplitude and is phase-shifted from a grid frequencyproportional to a difference between a measured grid frequency and anominal grid frequency.
 15. A system for generating power, comprising: aplurality of power sources; and a plurality of power converters, coupledto one another via an AC line and coupled to the plurality of powersources in a one-to-one correspondence, wherein each power converter ofthe plurality of power converters comprises a controller for controllingan instantaneous current generated by the power converter such that thatpower converter appears, from the perspective of the AC line coupled tothe power converter, as a virtual AC voltage source in series with avirtual impedance.
 16. The system of claim 15, wherein real and reactivephasor currents for the power converter are indirectly controlled. 17.The system of claim 16, wherein the real and reactive phasor currentthresholds are indirectly controlled by modifying amplitude and phase ofa virtual voltage waveform that defines the virtual AC voltage source.18. The system of claim 15, wherein the power converter is controlled toimitate the virtual AC voltage source in series with the virtualimpedance independent of whether the power converter is islanded orgrid-connected.
 19. The system of claim 15, wherein (i) when the powerconverter is islanded, the power converter is controlled to imitate thevirtual AC voltage source in series with the virtual impedanceindependent of whether the power converter is islanded orgrid-connected, and (ii) when the power converter is grid-connected, thepower converter is controlled by a different control technique.
 20. Thesystem of claim 15, wherein a virtual voltage waveform representing thevirtual AC voltage source is derived using a phase-shift virtualimpedance droop technique where the virtual AC voltage source is definedas a sinusoidal voltage source having a constant amplitude and isphase-shifted from a grid frequency proportional to a difference betweena measured grid frequency and a nominal grid frequency.